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19-2834; Rev 0; 4/03
155Mbps Low-Noise Transimpedance Amplifier
General Description
The MAX3657 is a transimpedance preamplifier for receivers operating up to 155Mbps. The low noise, high gain, and low power dissipation make it ideal for Class-B and Class-C passive optical networks (PON). The circuit features 14nA input-referred noise, 130MHz bandwidth, and 2mA input overload. Low jitter is achieved without external compensation capacitors. Operating from a +3.3V supply, the MAX3657 consumes only 76mW power. An integrated filter resistor provides positive bias for the photodiode. These features, combined with a small die size, allow easy assembly into a TO-46 header with a photodiode. The MAX3657 includes an average photocurrent monitor. The MAX3657 has a typical optical sensitivity of -38dBm (0.9A/W), which exceeds the Class-C PON requirements. Typical overload is 0dBm. The MAX3657 is available in die and 3mm x 3mm 12-pin QFN packages. o 14nARMS Input-Referred Noise o 54k Transimpedance Gain o 130MHz (typ) Bandwidth o 2mAP-P Input Current--0dBm Overload Capability o 76mW (typ) Power Dissipation o 3.3V Single-Supply Operation o Average Photocurrent Monitor
Features
MAX3657
Ordering Information
PART MAX3657EGG* MAX3657E/D TEMP RANGE -40C to +85C -40C to +85C PIN-PACKAGE 12 QFN Die**
Applications
Optical Receivers (Up to 155Mbps Operation) Passive Optical Networks (PON) SFP/SFF Transceivers BiDi Transceivers
*Future product--contact factory for availability. **Dice are designed to operate over a -40C to +110C junction temperature (TJ) range, but are tested and guaranteed at TA = +25C. Pin Configuration appears at end of data sheet.
Typical Application Circuit
3.3V CVCC1
CVCC2
VCCZ RFILT FILT CFILT IN
VCC
OUT+
1F
MAX3964
COUT OUT1F RLOAD 200
LIMITING AMPLIFIER
MAX3657
GND MON
TO-46 HEADER
RMON* *OPTIONAL COMPONENT
________________________________________________________________ Maxim Integrated Products
1
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
ABSOLUTE MAXIMUM RATINGS
Power-Supply Voltage ...........................................-0.5V to +6.0V Input Continuous Current ................................................3.5mA Voltage at OUT+, OUT- ...................(VCC - 1.5V) to (VCC + 0.5V) Voltage at FILT, MON .................................-0.5V to (VCC + 0.5V) Continuous Power Dissipation 12-Pin QFN (derate 14.7mW/C above +70C) ...........1176mW Operating Temperature Range 12-Pin QFN ........................................................-40C to +85C Operating Junction Temperature Range Die .................................................................-40C to +150C Storage Temperature Range .............................-55C to +150C Lead Temperature (soldering, 10s) .................................+300C Die Attach Temperature...................................................+400C
Stresses beyond those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
DC ELECTRICAL CHARACTERISTICS
(VCC1 = +2.97V to +3.63V, 200 load between OUT+ and OUT-, TA = -40C to +85C. Typical values are at VCC = +3.3V, TA = +25C, unless otherwise noted.) (Note 1)
PARAMETER Supply Current Input Bias Voltage Transimpedance Linear Range Small-Signal Transimpedance Output Common-Mode Voltage Output Resistance (Per Side) Maximum Differential Output Voltage Filter Resistor DC Input Overload Monitor Nominal Gain Monitor Gain Stability (Die Only, Note 3) GNOM VCC = +3.3V, +25C (Note 2) IIN = 100A to 1mA G IIN = 5A IIN = 2A IIN = 1A ROUT RFILT Z21 SYMBOL ICC VIN IIN 1mA 0.95 < linearity < 1.05, referred to gain at 1AP-P input Differential output, IIN < 200nAP-P AC-coupled outputs Single-ended output resistance 85 170 640 1 0.8 -1.5 -1.5 -4.0 2.0 2 44 54 VCC 0.225 100 250 800 1.5 1 1.2 +1.5 +2.2 +3.4 dB 115 450 960 65 CONDITIONS MIN TYP 23 1 MAX 34 1.3 UNITS mA V AP-P k V mVP-P mA A/A
VOUT(max) IIN = 2mAP-P, VOUT = (VOUT+) - (VOUT-)
AC ELECTRICAL CHARACTERISTICS
(VCC = +2.97V to +3.63V, 200 load between OUT+ and OUT-, CIN = 0.5pF, CFILT = 400pF, CVCC2 = 680pF, TA = -40C to +85C. Typical values are at VCC = +3.3V, TA = +25C, unless otherwise noted.) (Note 1)
PARAMETER Small-Signal Bandwidth Low-Frequency Cutoff AC Overload Pulse-Width Distortion Input-Referred Noise Current RMS Noise Density Monitor Bandwidth PWD In 300nAP-P IIN 2mAP-P f = 100MHz (Note 4) f = 117MHz f = 100MHz IIN = 1A 14 1.3 5 SYMBOL BW-3dB CONDITIONS Relative to gain at 1MHz -3dB, IIN = 1A 2 22 15 MIN 110 TYP 130 5 25 MAX UNITS MHz kHz mAP-P psP-P nARMS pA/Hz kHz
2
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155Mbps Low-Noise Transimpedance Amplifier
AC ELECTRICAL CHARACTERISTICS (12-PIN QFN)
(VCC = +2.97V to +3.63V, RLOAD = 200, CIN = 1.0pF, CFILT = 1000pF, CVCC2 = 0.01F, TA = -40C to +85C. Typical values are at VCC = +3.3V, TA = +25C, unless otherwise noted.) (Note 1)
PARAMETER Small-Signal Bandwidth Low-Frequency Cutoff AC Overload Pulse-Width Distortion Input-Referred Noise Current RMS Noise Density PWD In 1AP-P IIN 2mAP-P f = 50MHz (Note 4) f = 100MHz f = 100MHz SYMBOL BW-3dB CONDITIONS Relative to gain at 1MHz -3dB, IIN = 1A 2 22 5 13 1.3 MIN TYP 95 5 25 MAX UNITS MHz kHz mA psP-P nARMS pA/Hz
MAX3657
Note 1: Die parameters are production tested at room temperature only, but are guaranteed by design from TA = -40C to +85C. AC characteristics guaranteed by design and characterization. Note 2: GNOM = [IMON (1mA) - IMON (5A)] / [ (1mA) - (5A)]. Note 3: Stability is relative to the nominal gain at VCC = +3.3V, TA = +25C. G(IIN) dB = 10 log10 [ IMON(IIN) ] / [ IMON(1mA) - GNOM x (1mA - IIN)], VMON 2.1V, Input tr, tf > 550ps (20% to 80%). Note 4: Total noise integrated from 0 to f.
Typical Operating Characteristics
(MAX3657 E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25C, unless otherwise noted.)
SMALL-SIGNAL TRANSIMPEDANCE vs. TEMPERATURE
MAX3657 toc01
SUPPLY CURRENT vs. TEMPERATURE
90 80 SUPPLY CURRENT (mA) 70 60 50 40 30 20 10
MAX3657 toc02
INPUT BIAS VOLTAGE vs. TEMPERATURE
MAX3657 toc03
60 0.2AP-P TRANSIMPEDANCE GAIN (k) 55
100
1.3 1.2 INPUT BIAS VOLTAGE (V) 1.1 1.0 0.9 0.8 0.7
50
1.0AP-P
45
40
35 -40 -20 60 AMBIENT TEMPERATURE (C) 0 20 40 80
0 -40 -20 60 AMBIENT TEMPERATURE (C) 0 20 40 80
-40
-20
0
20
40
60
80
AMBIENT TEMPERATURE (C)
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
Typical Operating Characteristics (continued)
(MAX3657 E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25C, unless otherwise noted.)
PULSE-WIDTH DISTORTION vs. INPUT CURRENT AMPLITUDE
MAX3657 toc04
DIFFERENTIAL OUTPUT VOLTAGE vs. INPUT CURRENT
300 OUTPUT VOLTAGE (mVP-P) 200 100 0 -100 -200 -300 VFILT = GND -400 80 -20 -15 -10 -5 0 5 10 15 20 100 1k RLOAD = 100 Z21 = 36k RLOAD = OPEN Z21 = 108k RLOAD = 200 Z21 = 54k
MAX3657 toc05
FREQUENCY RESPONSE
MAX3657 toc06
100 90 PULSE-WIDTH DISTORTION (ps) 80 70 60 50 40 30 20 10 0 0.1 1.0 10 100 1000 +85C -40C +25C
400
98 95 OUTPUT MAGNITUDE (dB) 92 DIFFERENTIAL OUTPUT
89 86 83 SINGLE-ENDED OUTPUT
10,000
10k
100k
1M
10M 100M
1G
INPUT SIGNAL AMPLITUDE (A)
INPUT CURRENT (A)
FREQUENCY (Hz)
BANDWIDTH vs. CAPACITANCE
MAX3657 toc07
INPUT-REFERRED RMS NOISE vs. CAPACITANCE
MAX3657 toc08
INPUT-REFERRED RMS NOISE vs. DC INPUT CURRENT
TJ = +110C INPUT-REFERRED NOISE (nARMS) 1.0 0.8 0.6 0.4 0.2 0 TJ = +25C TJ = -40C
MAX3657 toc09
275 250 225 200 BANDWIDTH (MHz) 175 150 125 100 75 50 25 0 0.1 0.3 0.5 0.7 0.9 1.1 1.3 TJ = -40C TJ = +25C TJ = +110C
35 INPUT-REFERRED NOISE (nARMS) 30 25 20 TJ = +110C 15 10 0 TJ = -40C
1.2
TJ = +25C
1.5
0.2
0.4
0.6
0.8
1.0
1.2
1.4
0.1
1.0
10
100
1000
10,000
CAPACITANCE (pF)
CAPACITANCE (pF)
DC CURRENT IN (A)
OUTPUT EYE DIAGRAM (1.0A ELECTRICAL INPUT)
50mV
MAX3657 toc10
OUTPUT EYE DIAGRAM (100A ELECTRICAL INPUT)
200mV
MAX3657 toc11
OUTPUT EYE DIAGRAM (1mA ELECTRICAL INPUT)
200mV
MAX3657 toc12
10mV
40mV
40mV
-50mV 1ns/div
-200mV 1ns/div
-200mV 1ns/div
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155Mbps Low-Noise Transimpedance Amplifier
Typical Operating Characteristics (continued)
(MAX3657 E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25C, unless otherwise noted.)
OUTPUT EYE DIAGRAM (-30dBm OPTICAL INPUT)
MAX3657toc13
MAX3657
OUTPUT EYE DIAGRAM (-1dBm OPTICAL INPUT)
MAX3657toc14
INPUT IMPEDANCE vs. FREQUENCY
MAGNITUDE OF INPUT IMPEDANCE () 750 700 650 600 550 500 450 400 350 300 100 1k 10k 100k 1M 10M 100M 1G FREQUENCY (Hz) TJ = +110C SMALL SIGNAL TJ = +25C TJ = -40C
MAX3657 toc15
800
6mV/ div 223-1 PRBS 20mV/ div 223-1 PRBS
ZARLINK 1A358 PHOTODIODE + MAX3657 1ns/div
ZARLINK 1A358 PHOTODIODE + MAX3657 1ns/div
Pin Description
PIN 1, 9, 11 2 3 4 5 6 7 8 10 12 NAME N.C. GND GNDZ MON IN FILT VCCZ VCC OUT+ OUTNo Connection. Do not connect. Negative Supply Voltage. Both GND and GNDZ must be connected to ground. Negative Supply Voltage. Both GND and GNDZ must be connected to ground. Photocurrent Monitor. This is a current output. Connect a resistor between MON and ground to monitor the average photocurrent. Signal Input. Connect to photodiode anode. Filter Connection (Optional). Use to bias the photodiode cathode. An internal 800 on-chip resistor is connected between this pin and VCCZ , an external decoupling capacitor connected to this pin forms a filter (see the Design Procedure section). Power-Supply Voltage. Both VCC and VCCZ must be connected to the supply. Power-Supply Voltage. Both VCC and VCCZ must be connected to the supply. Positive Data Output. This output has 100 back termination, increasing input current causes OUT+ to increase. Negative Data Output. This output has 100 back termination, increasing input current causes OUT- to decrease. FUNCTION
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
Functional Diagram
MAX3657
TRANSIMPEDANCE AMPLIFIER IN VOLTAGE AMPLIFIER OUTPUT BUFFER
RF
ROUT OUT+ OUTROUT
+1.0V DC-CANCELLATION CIRCUIT LOWPASS FILTER MON VCCZ ROUT FILT ENABLE
Detailed Description
The MAX3657 transimpedance amplifier is designed for 155Mbps fiber optic applications. The functional diagram of the MAX3657 is comprised of a transimpedance amplifier, a voltage amplifier, a DC-cancellation circuit, and a CML output buffer.
do not drive a DC-coupled grounded load. The outputs should be AC-coupled or terminated to VCC. If a singleended output is required, both the used and the unused outputs should be terminated in a similar manner.
DC-Cancellation Circuit
The DC-cancellation circuit uses low-frequency feedback to remove the DC component of the input signal (Figure 2). This feature centers the input signal within the transimpedance amplifier's linear range, thereby reducing pulse-width distortion. The DC-cancellation circuit is internally compensated and does not require external capacitors. This circuit minimizes pulse-width distortion for data sequences that exhibit a 50% mark density. A mark density significantly different from 50% causes the MAX3657 to generate pulse-width distortion. Grounding the FILT pin disables the DC-cancellation circuit. For normal operation, the DC-cancellation circuit must be enabled. The DC-cancellation current is drawn from the input and creates noise. For low-level signals with little or no DC component, the added noise is insignificant. However, amplifier noise increases for signals with significant DC component (see the Typical Operating Characteristics).
Transimpedance Amplifier
The signal current at the input flows into the summing node of a high-gain amplifier. Shunt feedback through resistor RF converts this current into a voltage. Schottky diodes clamp the output signal for large input currents (Figure 1).
Voltage Amplifier
The voltage amplifier provides additional gain and converts the transimpedance amplifier single-ended output signal into a differential signal.
Output Buffer
The output buffer provides a reverse-terminated voltage output and is designed to drive a 200 differential load between OUT+ and OUT-. For optimum supplynoise rejection, the MAX3657 should be terminated with a differential load. The MAX3657 single-ended outputs
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
AMPLITUDE AMPLITUDE INPUT FROM PHOTODIODE
TIME OUTPUT (SMALL SIGNALS) INPUT AFTER DC CANCELLATION OUTPUT (LARGE SIGNALS)
TIME
Figure 1. MAX3657 Limited Outputs
Figure 2. Effects of DC Cancellation on Input
Photocurrent Monitor
The MAX3657 includes an average photocurrent monitor. The current at MON is approximately equal to the DC current at IN. Best monitor accuracy is obtained when data input edge time is longer than 500ps.
Select RMON
Connect a resistor between MON and ground to monitor the average photocurrent. Select RMON as large as possible: RMON = 2.1V IMONMAX
Design Procedure
Select Photodiode
Noise performance and bandwidth are adversely affected by stray capacitance on the TIA input node. Select a low-capacitance photodiode to minimize the total input capacitance on this pin. The MAX3657 is optimized for 0.5pF of capacitance on the input. Assembling the MAX3657 in die form using chip and wire technology provides the lowest capacitance input and the best possible performance.
where IMONMAX is the largest average input current observed.
Select Coupling Capacitors
A receiver built with the MAX3657 has a bandpass frequency response. The low-frequency cutoff due to the coupling capacitors and load resistors is: LFCTERM = 1 2 x RLOAD x CCOUPLE
Select CFILT
Supply voltage noise at the cathode of the photodiode produces a current I = CPD V/t, which reduces the receiver sensitivity (C PD is the photodiode capacitance). The filter resistor of the MAX3657, combined with an external capacitor, can be used to reduce the noise (see the Typical Application Circuit). Current generated by supply-noise voltage is divided between CFILT and CPD. To obtain a good optical sensitivity, select CFILT > 400pF.
Select CCOUPLE so the low-frequency cutoff due to the load resistors and coupling capacitors is much lower than the low-frequency cutoff of the MAX3657. The coupling capacitor should be 0.1F or larger, but 1.0F is recommended for lowest jitter. Refer to Maxim Application Note HFAN-1.1: Choosing AC-Coupling Capacitors for more information.
Layout Considerations
Figure 3 shows a suggested layout for a TO header for the MAX3657.
Select Supply Filter
The MAX3657 requires wideband power-supply decoupling. Power-supply bypassing should provide low impedance between VCC and ground for frequencies between 10kHz and 200MHz. Use LC filtering at the main supply terminal and decoupling capacitors as close to the die as possible.
Wire Bonding
For high-current density and reliable operation, the MAX3657 uses gold metalization. For best results, use gold-wire ball-bonding techniques. Use caution if attempting wedge bonding. Die-size is 41 mils x 48 mils, (1040m x 1220m) and die thickness is 15 mils (380m). The bond pad is 94.4m x 94.4m and its metal thickness is 1.2m. Refer to Maxim Application Note HFAN- 8.0.1:
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
CASE CFILT CVCC
4-PIN TO HEADER
FILT VCC Z VC C IN MO N
GN GN OU T+ OU T-
DZ
D
PHOTODIODE CASE IS GROUND
CASE
CFILT
CVCC 5-PIN TO HEADER
FILT VCCZ VCC
IN MON
GNDZ GND
OUT+
OUT-
PHOTODIODE CASE IS GROUND
Figure 3. Suggested TO Header Layout
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155Mbps Low-Noise Transimpedance Amplifier
Understanding Bonding Coordinates and Physical Die Size for more information on bond-pad coordinates.
Table 1. Optical Power Relations*
PARAMETER Average Power Extinction Ratio Optical Power of a 1 Optical Power of a 0 Optical Modulation Amplitude SYMBOL PAVG re P1 RELATION PAVG = (P0 + P1)/2 re = P1/P0
re r P1 P1 ==2PAVG re + 1 e 2PAVG re + 1
MAX3657
Applications Information
Optical Power Relations
Many of the MAX3657 specifications relate to the inputsignal amplitude. When working with optical receivers, the input is sometimes expressed in terms of average optical power and extinction ratio. Figure 4 and Table 1 show relations that are helpful for converting optical power to input signal when designing with the MAX3657.
P0
P0 = 2PAVG/(re + 1)
Optical Sensitivity Calculation
The input-referred RMS noise current (i n ) of the MAX3657 generally determines the receiver sensitivity. To obtain a system bit-error rate (BER) of 1E-10, the signal-to-noise ratio must always exceed 12.7. The input sensitivity, expressed in average power, can be estimated as:
12.7 x in x (re + 1) Sensitivity = 10log x 1000 dBm 2 x x (re - 1)
PIN
PIN = P1 - P0 = re 2PAVG re + 1
r -1 PIN = P1 - P0 = 2PAVG e re + 1
*Assuming a 50% average mark density.
Actual results may vary depending on supply noise, output filter, limiting amplifier sensitivity, and other factors (refer to Maxim Application Note HFAN-3.0.0: Accurately Estimating Optical Receiver Sensitivity).
where is the photodiode responsivity in A/W and in is the RMS noise current in amps. For example, with photodiode responsivity of 0.9A/W, an extinction ratio of 10 and 15nA input-referred noise, the sensitivity of the MAX3657 is:
12.7 x 15nA x 11 Sensitivity = 10log x 1000 dBm = - 38dBm 2 x 0.9A / W x 9
Input Optical Overload
Overload is the largest input the MAX3657 accepts while meeting the pulse-width distortion specification. Optical overload can be estimated in terms of average power with the following equation: 2mA Overload = 10log x 1000 dBm 2x For example, if photodiode responsitivity is 1.0A/W, the input overload is 0dBm.
Optical Linear Range
P1
The MAX3657 has high gain, which limits the output for large input signals. The MAX3657 operates in a linear range for inputs not exceeding:
2A (re + 1) Linear Range = 10log x 1000 dBm 2 x (re - 1)
OPTICAL POWER
PAVG
For example, with photodiode responsivity of 0.9A/W and an extinction ratio of 10 the linear range is:
P0
TIME
2A x 11 Linear Range = 10log x 1000 dBm = - 28dBm 2 x 0.9 x 9
Figure 4. Optical Power Relations
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
Interface Schematics
Equivalent Output Interface
The MAX3657 has a differential CML output structure with 100 back termination (200 differentially). Figure 5 is a simplified diagram of the output interface. The output current is divided between the internal 100 resistor and the external load resistance. Because of the CML structure, the maximum output-signal amplitude is affected by load impedance. Note that the internal back termination is 100 single ended and external termination is recommended to interface the device to 50 test equipment. For example, if single-ended operation in a 50 system is required, first match the output of the MAX3657 to the 50 controlled impedance by placing a 100 pullup resistor in parallel with the output. Then establish similar loading conditions on the unused output. Note that the loading conditions affect the overall gain of the MAX3657. Figures 6a, 6b, and 6c show alternate interface schemes for the MAX3657.
Pad Coordinates
Table 2 lists center-pad coordinates for the MAX3657 bond pads. Refer to Maxim Application Note HFAN8.0.1: Understanding Bonding Coordinates and Physical Die Size for more information on bond-pad coordinates.
VCC VCC ROUT 100 ROUT 100 OUT+ VCC
Table 2. Bond-Pad Information
PAD BP1 BP2 BP3 BP4
OUT-
NAME OUTGND GNDZ MON IN FILT N.C. VCCZ VCC OUT+ N.C.
COORDINATES X 47.2 52.2 52.2 395.5 522.3 648.5 808.5 808.5 808.5 808.5 741.1 Y 994.8 484.6 357.7 47.2 47.2 47.2 49.9 176.8 303.7 994.8 859.9
BP5 BP6 BP7 BP8 BP9 BP10 BP11
4.5mA
Figure 5. Equivalent Output Interface
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
VCC
100
100
100
100 50
50
50
50 L
DIFFERENTIAL CML INPUT STAGE
MAX3657
CML OUTPUT STAGE *COMPONENT NOT REQUIRED IF L < 10cm
Figure 6a. 50 DC-Coupled Interface
VCC
100 100 100
50
100
50
50 L
SINGLE-ENDED INPUT STAGE
MAX3657
CML OUTPUT STAGE NOTE: THE PARALLEL COMBINATION AT THE UNUSED OUTPUT CAN BE REPLACED BY A SINGLE EQUIVALENT 33 RESISTOR. *COMPONENT NOT REQUIRED IF L < 10cm
Figure 6b. 50 DC-Coupled Single-Ended Output Interface
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
VCC
100 100 100
100
50
50 L 50
50 LOAD TO GROUND
MAX3657
CML OUTPUT STAGE *COMPONENT NOT REQUIRED IF L < 10cm
Figure 6c. 50 AC-Coupled Single-Ended Output Interface
VCC
VCC
800 FILT
MON
Figure 7. FILT Interface
Figure 8. MON Interface
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155Mbps Low-Noise Transimpedance Amplifier
Chip Topography
TOP VIEW
OUT1 10
Pin Configuration
OUT12 N.C. 11 OUT+ 10
MAX3657
OUT+
11
N.C.
N.C. GND
GND GNDZ 0.048in 1.219mm
1 2 3
9 8 7
N.C. VCC VCCZ
MAX3657
2
GNDZ
3 9
VCC VCCZ
4 MON
5 IN
6 FILT
8
12 QFN
4
5
6
7
MON 0.041in 1.041mm
IN
FILT
N.C.
Chip Information
TRANSISTOR COUNT: 417 PROCESS: Silicon Bipolar SUBSTRATE: Connected to GND DIE SIZE: 1.04mm x 1.22mm
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155Mbps Low-Noise Transimpedance Amplifier MAX3657
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to www.maxim-ic.com/packages.
PACKAGE OUTLINE, 12,16L QFN, 3x3x0.90 MM
21-0102
G
1 2
14
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12, 16L QFN.EPS
155Mbps Low-Noise Transimpedance Amplifier
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to www.maxim-ic.com/packages.
MAX3657
PACKAGE OUTLINE, 12,16L QFN, 3x3x0.90 MM
21-0102
G
1 2
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 15 (c) 2003 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.

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